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MOTOROLA
SEMICONDUCTOR TECHNICAL DATA
Order this document by MC145200/D
2.0 GHz PLL Frequency Synthesizers
MC145200 MC145201
Include On-Board 64/65 Prescalers
The MC145200 and MC145201 are single-package synthesizers with serial interfaces capable of direct usage up to 2.0 GHz. A special architecture makes these PLLs very easy to program because a byte-oriented format is utilized. Due to the patented BitGrabberTM registers, no address/steering bits are required for random access of the three registers. Thus, tuning can be accomplished via a 3-byte serial transfer to the 24-bit A register. The interface is both SPI and MICROWIRETM compatible. Each device features a single-ended current source/sink phase detector output and a double-ended phase detector output. Both phase detectors have linear transfer functions (no dead zones). The maximum current of the single-ended phase detector output is determined by an external resistor tied from the Rx pin to ground. This current can be varied via the serial port. The MC145200 features logic-level converters and high-voltage phase/ frequency detectors; the detector supply may range up to 9.5 V. The MC145201 has lower-voltage phase/frequency detectors optimized for single-supply systems of 5 V 10%. Each part includes a differential RF input which may be operated in a single-ended mode. Also featured are on-board support of an external crystal and a programmable reference output. The R, A, and N counters are fully programmable. The C register (configuration register) allows the parts to be configured to meet various applications. A patented feature allows the C register to shut off unused outputs, thereby minimizing system noise and interference. In order to have consistent lock times and prevent erroneous data from being loaded into the counters, on-board circuitry synchronizes the update of the A register if the A or N counters are loading. Similarly, an update of the R register is synchronized if the R counter is loading. The double-buffered R register allows new divide ratios to be presented to the three counters (R, A, and N) simultaneously. * Maximum Operating Frequency: 2000 MHz @ Vin = 200 mV p-p * Operating Supply Current: 12 mA Nominal * Operating Supply Voltage Range (VDD and VCC Pins): 4.5 to 5.5 V * Operating Supply Voltage Range of Phase Detectors (VPD Pin) -- MC145200: 8.0 to 9.5 V MC145201: 4.5 to 5.5 V * Current Source/Sink Phase Detector Output Capability: 2 mA Maximum * Gain of Current Source/Sink Phase/Frequency Detector Controllable via Serial Port * Operating Temperature Range: - 40 to + 85C * R Counter Division Range: (1 and) 5 to 8191 * Dual-Modulus Capability Provides Total Division up to 262,143 * High-Speed Serial Interface: 4 Mbps * OUTPUT A Pin, When Configured as Data Out, Permits Cascading of Devices * Two General-Purpose Digital Outputs -- OUTPUT A: Totem-Pole (Push-Pull) OUTPUT B: Open-Drain * Power-Saving Standby Feature with Orderly Recovery for Minimizing Lock Times, Standby Current: 30 A * Evaluation Kit Available (Part Numbers MC145200EVK and MC145201EVK) * See Application Note AN1253/D for Low-Pass Filter Design, and AN1277/D for Offset Reference PLLs for Fine Resolution or Fast Hopping
20
F SUFFIX SOG PACKAGE CASE 751J
1
20 1
DT SUFFIX TSSOP CASE 948D
ORDERING INFORMATION
MC145200F MC145201F MC145200DT MC145201DT SOG Package SOG Package TSSOP TSSOP
PIN ASSIGNMENT
REFout LD R V VPD PDout GND Rx TEST 1 fin 1 2 3 4 5 6 7 8 9 10 20 19 18 17 16 15 14 13 12 11 REFin Din CLK ENB OUTPUT A OUTPUT B VDD TEST 2 VCC fin
BitGrabber is a trademark of Motorola, Inc. MICROWIRE is a trademark of National Semiconductor Corp.
REV 4 1/98 TN98012300
(c) Motorola, Inc. 1998 MOTOROLA
MC145200*MC145201 1
BLOCK DIAGRAM
DATA OUT REFin 20 OSC OR 4-STAGE DIVIDER (CONFIGURABLE) 3 13-STAGE R COUNTER fR PORT fV 13 DOUBLE-BUFFERED BitGrabberTM R REGISTER 16 BITS SELECT LOGIC 16 OUTPUT A
REFout
1
LOCK DETECTOR AND CONTROL
2
LD
CLK Din
18 19 SHIFT REGISTER AND CONTROL LOGIC BitGrabberTM C REGISTER 8 BITS
8 PHASE/FREQUENCY DETECTOR A AND CONTROL 6
Rx
24
PDout
ENB
17
STANDBY LOGIC
POR 2 PHASE/FREQUENCY DETECTOR B AND CONTROL 3 R 4 V
BitGrabberTM A REGISTER 24 BITS INTERNAL CONTROL 6 4 6-STAGE A COUNTER 12 12-STAGE N COUNTER 15 OUTPUT B (OPEN-DRAIN OUTPUT)
fin fin
11 10 INPUT AMP 64/65 PRESCALER MODULUS CONTROL LOGIC 13 TEST 2 9 TEST 1
SUPPLY CONNECTIONS: PIN 12 = VCC (V+ TO INPUT AMP AND 64/65 PRESCALER) PIN 5 = VPD (V+ TO PHASE/FREQUENCY DETECTORS A AND B) PIN 14 = VDD (V+ TO BALANCE OF CIRCUIT) PIN 7 = GND (COMMON GROUND)
MAXIMUM RATINGS* (Voltages Referenced to GND, unless otherwise stated)
Symbol VCC, VDD VPD Vin Vout Vout Iin, IPD Iout IDD PD Tstg TL Parameter DC Supply Voltage (Pins 12 and 14) DC Supply Voltage (Pin 5) DC Input Voltage DC Output Voltage (except OUTPUT B, PDout, R, V) DC Output Voltage (OUTPUT B, PDout, R, V) DC Input Current, per Pin (Includes VPD) DC Output Current, per Pin DC Supply Current, VDD and GND Pins Power Dissipation, per Package Storage Temperature Lead Temperature, 1 mm from Case for 10 seconds MC145200 MC145201 Value - 0.5 to + 6.0 VDD - 0.5 to + 9.5 VDD - 0.5 to + 6.0 - 0.5 to VDD + 0.5 - 0.5 to VDD + 0.5 - 0.5 to VPD + 0.5 10 20 30 300 - 65 to + 150 260 Unit V V V V V mA mA mA mW C C This device contains protection circuitry to guard against damage due to high static voltages or electric fields. However, precautions must be taken to avoid applications of any voltage higher than maximum rated voltages to this high-impedance circuit.
* Maximum Ratings are those values beyond which damage to the device may occur. Functional operation should be restricted to the limits in the Electrical Characteristics tables or Pin Descriptions section.
MC145200*MC145201 2
MOTOROLA
ELECTRICAL CHARACTERISTICS
(VDD = VCC = 4.5 to 5.5 V, Voltages Referenced to GND, TA = - 40 to + 85C, unless otherwise stated; MC145200: VPD = 8.0 to 9.5 V; MC145201: VPD = 4.5 to 5.5 V with VDD VPD.) Symbol VIL VIH Vhys VOL VOH IOL IOH IOL IOH Iin Iin IOZ IOZ ISTBY Parameter Maximum Low-Level Input Voltage (Din, CLK, ENB, REFin) Minimum High-Level Input Voltage (Din, CLK, ENB, REFin) Minimum Hysteresis Voltage (CLK, ENB) Maximum Low-Level Output Voltage (REFout, OUTPUT A) Minimum High-Level Output Voltage (REFout, OUTPUT A) Minimum Low-Level Output Current (REFout, LD, R, V) Minimum High-Level Output Current (REFout, LD, R, V) Minimum Low-Level Output Current (OUTPUT A, OUTPUT B) Minimum High-Level Output Current (OUTPUT A Only) Maximum Input Leakage Current (Din, CLK, ENB, REFin) Maximum Input Current (REFin) Maximum Output Leakage Current Iout = 20 A, Device in Reference Mode Iout = -20 A, Device in Reference Mode Vout = 0.4 V Vout = VDD - 0.4 V for REFout, LD Vout = VPD - 0.4 V for R, V Vout = 0.4 V Vout = VDD - 0.4 V Vin = VDD or GND, Device in XTAL Mode Vin = VDD or GND, Device in Reference Mode (PDout) Vout = VPD - 0.5 or 0.5 V Output in High-Impedance State MC145200 MC145201 Test Condition Device in Reference Mode, DC Coupled Device in Reference Mode, DC Coupled Guaranteed Limit 0.3 x VDD 0.7 x VDD 300 0.1 VDD - 0.1 0.36 - 0.36 1.0 - 0.6 1.0 150 150 200 10 30 Unit V V mV V V mA mA mA mA A A nA A A
Maximum Output Leakage Current Vout = VPD or GND, (OUTPUT B) Output in High-Impedance State Maximum Standby Supply Current (VDD + VPD Pins) Vin = VDD or GND; Outputs Open; Device in Standby Mode, Shut-Down Crystal Mode or REFout-Static-Low Reference Mode; OUTPUT B Controlling VCC per Figure 22 Bit C6 = High Which Selects Phase Detector A, PDout = Open, PDout = Static Low or High, Bit C4 = Low Which is not Standby, IRx = 113 A Bit C6 = Low Which Selects Phase Detector B, R and V = Open, R and V = Static Low or High, Bit C4 = Low Which is not Standby
IPD
Maximum Phase Detector Quiescent Current (VPD Pin)
600
A
30
IT
Total Operating Supply Current (VDD + VPD + VCC Pins)
fin = 2.0 GHz; REFin = 13 MHz @ 1 V p-p; OUTPUT A = Inactive and No Connect; REFout, V, R, PDout, LD = No Connect; Din, ENB, CLK = VDD or GND, Phase Detector B Enabled (Bit C6 = Low)
*
mA
* The nominal value = 12 mA. This is not a guaranteed limit.
MOTOROLA
MC145200*MC145201 3
ANALOG CHARACTERISTICS--CURRENT SOURCE/SINK OUTPUT--PDout
(Iout 2 mA, VDD = VCC = 4.5 to 5.5 V, VDD VPD. Voltages Referenced to GND) Parameter Maximum Source Current Variation Guaranteed Limit 20 20 20 20 12 12 12 12 0.5 to 7.5 0.5 to 9.0 0.5 to 4.0 0.5 to 5.0 V V % % %
Test Condition MC145200: Vout = 0.5 x VPD MC145201: Vout = 0.5 x VPD MC145200: Vout = 0.5 x VPD MC145201: Vout = 0.5 x VPD MC145200: Iout variation 20% MC145201: Iout variation 20%
VPD 8.0 9.5 4.5 5.5
Unit %
Maximum Sink-vs-Source Mismatch (Note 3)
8.0 9.5 4.5 5.5
Output Voltage Range (Note 3)
8.0 9.5 4.5 5.5
NOTES: 1. Percentages calculated using the following formula: (Maximum Value - Minimum Value) / Maximum Value. 2. See Rx Pin Description for external resistor values. 3. This parameter is guaranteed for a given temperature within - 40 to + 85C.
AC INTERFACE CHARACTERISTICS (VDD = 4.5 to 5.5 V, TA = - 40 to + 85C, CL = 50 pF, Input tr = tf = 10 ns; MC145200: VPD = 8.0 to 9.5 V; MC145201: VPD = 4.5 to 5.5 V with VDD VPD)
Symbol fclk tPLH, tPHL tPLH, tPHL tPZL, tPLZ tTLH, tTHL Cin Parameter Serial Data Clock Frequency (Note: Refer to Clock tw below) Maximum Propagation Delay, CLK to OUTPUT A (Selected as Data Out) Maximum Propagation Delay, ENB to OUTPUT A (Selected as Port) Maximum Propagation Delay, ENB to OUTPUT B Maximum Output Transition Time, OUTPUT A and OUTPUT B; tTHLonly, on OUTPUT B Maximum Input Capacitance - Din, ENB, CLK, Figure No. 1 1, 5 2, 5 2, 6 1, 5, 6 Guaranteed Limit dc to 4.0 105 100 120 100 10 Unit MHz ns ns ns ns pF
TIMING REQUIREMENTS
(VDD = 4.5 to 5.5 V, TA = - 40 to + 85C, Input tr = tf = 10 ns unless otherwise indicated) Symbol tsu, th tsu, th, trec tw tw tr, tf Parameter Minimum Setup and Hold Times, Din vs CLK Minimum Setup, Hold and Recovery Times, ENB vs CLK Minimum Pulse Width, ENB Minimum Pulse Width, CLK Maximum Input Rise and Fall Times, CLK Figure No. 3 4 4 1 1 Guaranteed Limit 20 100 * 125 100 Unit ns ns cycles ns s
* The minimum limit is 3 REFin cycles or 195 fin cycles, whichever is greater.
MC145200*MC145201 4
MOTOROLA
SWITCHING WAVEFORMS
tf 90% CLK 50% 10% tw 1/fclk tPLH OUTPUT A (DATA OUT) 90% 50% 10% tTLH
tr VDD GND tw OUTPUT A tPHL tPLZ OUTPUT B tTHL tPZL 50% ENB 50% tPLH 50% tPHL VDD GND
10%
Figure 1.
Figure 2.
VALID VDD Din 50% GND tsu CLK th 50% GND tsu VDD CLK 50% FIRST CLK ENB 50%
tw
tw VDD GND th trec VDD LAST CLK GND
Figure 3.
Figure 4.
+V TEST POINT TEST POINT 7.5 k DEVICE UNDER TEST DEVICE UNDER TEST CL *
CL *
*Includes all probe and fixture capacitance.
Figure 5. Test Circuit
*Includes all probe and fixture capacitance.
Figure 6. Test Circuit
MOTOROLA
MC145200*MC145201 5
LOOP SPECIFICATIONS (VDD = VCC = 4.5 to 5.5 V unless otherwise indicated, TA = - 40 to + 85C)
Figure No. 7 8 Guaranteed Operating Range Min 200 13 6* 12 4.5* 2 dc dc fR in Phase with fV, CL = 50 pF, VPD = 5.5 V, VDD = VCC = 5.0 V CL = 50 pF, VPD = 5.5 V, VDD = VCC = 5.0 V fin REFin 11, 12 11, 12 17 -- -- -- Max 1500 27 27 27 27 15 10 2 85 65 TBD 5 Unit Ui mV p-p MHz
Symbol S bl Vin fref
Parameter P Input Voltage Range, fin Input Frequency, REFin Externally Driven in Reference Mode Crystal Frequency, Crystal Mode Output Frequency, REFout Operating Frequency of the Phase Detectors Output Pulse Width, LD, R, and V, -- MC145200, MC145201 Output Transition Times, LD, V, and R -- MC145201 Input Capacitance MC145200 MC145201
Test C di i T Condition 500 MHz fin 2000 MHz Vin 400 mV p-p Vin 1 V p-p Vin 400 mV p-p Vin 1 V p-p C1 30 pF, C2 30 pF, Includes Stray Capacitance CL = 30 pF
fXTAL fout f tw tTLH, tTHL Cin
9 10, 12
MHz MHz MHz ns ns pF
*If lower frequency is desired, use wave shaping or higher amplitude sinusoidal signal.
SINE WAVE GENERATOR
1000 pF fin 1000 pF Vin fin OUTPUT A DEVICE UNDER TEST (fv)
TEST POINT
SINE WAVE GENERATOR
0.01 F REFin OUTPUT A DEVICE UNDER TEST REFout VCC GND VDD V+ (fR)
TEST POINT
50 *
50 V+
Vin
VCC GND VDD
TEST POINT
*Characteristic Impedance
Figure 7. Test Circuit
Figure 8. Test Circuit-Reference Mode
C1
REFin OUTPUT A DEVICE UNDER TEST REFout VCC GND VDD
TEST POINT (fR)
C2
1/f REFout V+ REFout 50%
Figure 9. Test Circuit-Crystal Mode
Figure 10. Switching Waveform
MC145200*MC145201 6
MOTOROLA
TEST POINT tw OUTPUT 50% 90% 10% tTHL tTLH DEVICE UNDER TEST
CL *
*Includes all probe and
fixture capacitance.
Figure 11. Switching Waveform
Figure 12. Test Circuit
MC145200/MC145201 NORMALIZED INPUT IMPEDANCE AT fin -- SERIES FORMAT (R + jX) (500 MHz to 2 GHz)
fin (PIN 11) SOG PACKAGE
1
4 2 3
Marker 1 2 3 4
Frequency (GHz) 0.5 1 1.5 2
Resistance () 59.0 34.7 28.3 37.4
Capacitive Reactance () - 240 - 118 - 68.7 - 45.7
Capacitance (pF) 1.33 1.35 1.54 1.74
MOTOROLA
MC145200*MC145201 7
PIN DESCRIPTIONS
DIGITAL INTERFACE PINS Din Serial Data Input (Pin 19) The bit stream begins with the most significant bit (MSB) and is shifted in on the low-to-high transition of CLK. The bit pattern is 1 byte (8 bits) long to access the C or configuration register, 2 bytes (16 bits) to access the first buffer of the R register, or 3 bytes (24 bits) to access the A register (see Table 1). The values in the C, R, and A registers do not change during shifting because the transfer of data to the registers is controlled by ENB. CAUTION The value programmed for the N-counter must be greater than or equal to the value of the A-counter. The 13 least significant bits (LSBs) of the R register are double-buffered. As indicated above, data is latched into the first buffer on a 16-bit transfer. (The 3 MSBs are not double- buffered and have an immediate effect after a 16-bit transfer.) The second buffer of the R register contains the 13 bits for the R counter. This second buffer is loaded with the contents of the first buffer when the A register is loaded (a 24-bit transfer). This allows presenting new values to the R, A, and N counters simultaneously. If this is not required, then the 16-bit transfer may be followed by pulsing ENB low with no signal on the CLK pin. This is an alternate method of transferring data to the second buffer of the R register (see Figure 17). The bit stream needs neither address nor steering bits due to the innovative BitGrabber registers. Therefore, all bits in the stream are available to be data for the three registers. Random access of any register is provided. That is, the registers may be accessed in any sequence. Data is retained in the registers over a supply range of 4.5 to 5.5 V. The formats are shown in Figures 15, 16, and 17. Din typically switches near 50% of VDD to maximize noise immunity. This input can be directly interfaced to CMOS devices with outputs guaranteed to switch near rail-to-rail. When interfacing to NMOS or TTL devices, either a level shifter (MC74HC14A, MC14504B) or pull-up resistor of 1 k to 10 k must be used. Parameters to consider when sizing the resistor are worst-case IOL of the driving device, maximum tolerable power consumption, and maximum data rate. Table 1. Register Access
(MSBs are shifted in first; C0, R0, and A0 are the LSBs) Number of Clocks 8 16 24 Other Values 32 Values > 32 Accessed Register C Register R Register A Register See Figure 13 See Figures 22-25 Bit Nomenclature C7, C6, C5, . . ., C0 R15, R14, R13, . . ., R0 A23, A22, A21, . . ., A0
CLK Serial Data Clock Input (Pin 18) Low-to-high transitions on CLK shift bits available at the D in pin, while high-to-low transitions shift bits from OUTPUT A (when configured as Data Out, see Pin 16). The 24-1/2-stage shift register is static, allowing clock rates down to dc in a continuous or intermittent mode. Eight clock cycles are required to access the C register. Sixteen clock cycles are needed for the first buffer of the R register. Twenty-four cycles are used to access the A register. See Table 1 and Figures 15, 16, and 17. The number of clocks required for cascaded devices is shown in Figures 24 through 26. CLK typically switches near 50% of V DD and has a Schmitt-triggered input buffer. Slow CLK rise and fall times are allowed. See the last paragraph of Din for more information. NOTE To guarantee proper operation of the power-on reset (POR) circuit, the CLK pin must be held at GND (with ENB being a don't care) or ENB must be held at the potential of the V+ pin (with CLK being a don't care) during power-up. As an alternative, the bit sequence of Figure 13 may be used. ENB Active Low Enable Input (Pin 17) This pin is used to activate the serial interface to allow the transfer of data to/from the device. When ENB is in an inactive high state, shifting is inhibited and the port is held in the initialized state. To transfer data to the device, ENB (which must start inactive high) is taken low, a serial transfer is made via Din and CLK, and ENB is taken back high. The low-to-high transition on ENB transfers data to the C or A registers and first buffer of the R register, depending on the data stream length per Table 1. NOTE Transitions on ENB must not be attempted while CLK is high. This puts the device out of synchronization with the microcontroller. Resynchronization occurs when ENB is high and CLK is low. This input is also Schmitt-triggered and switches near 50% of VDD, thereby minimizing the chance of loading erroneous data into the registers. See the last paragraph of Din for more information. For POR information, see the note for the CLK pin. OUTPUT A Configurable Digital Output (Pin 16) OUTPUT A is selectable as fR, fV, Data Out, or Port. Bits A22 and A23 in the A register control the selection; see Figure 16. If A23 = A22 = high, OUTPUT A is configured as fR. This signal is the buffered output of the 13-stage R counter. The fR signal appears as normally low and pulses high, and can be used to verify the divide ratio of the R counter. This ratio extends from 5 to 8191 and is determined by the binary value loaded into bits R0 through R12 in the R register. Also, direct access to the phase detectors via the REFin pin is allowed by choosing a divide value of 1 (see Figure 17). The maximum frequency at which the phase detectors operate is 2 MHz. Therefore, the frequency of fR should not exceed 2 MHz.
MC145200*MC145201 8
MOTOROLA
If A23 = high and A22 = low, OUTPUT A is configured as fV. This signal is the buffered output of the 12-stage N counter. The fV signal appears as normally low and pulses high, and can be used to verify the operation of the prescaler, A counter, and N counter. The divide ratio between the fin input and the fV signal is N x 64 + A. N is the divide ratio of the N counter and A is the divide ratio of the A counter. These ratios are determined by bits loaded into the A register. See Figure 16. The maximum frequency at which the phase detectors operate is 2 MHz. Therefore, the frequency of fV should not exceed 2 MHz. If A23 = low and A22 = high, OUTPUT A is configured as Data Out. This signal is the serial output of the 24-1/2-stage shift register. The bit stream is shifted out on the high-to-low transition of the CLK input. Upon power up, OUTPUT A is automatically configured as Data Out to facilitate cascading devices. If A23 = A22 = low, OUTPUT A is configured as Port. This signal is a general-purpose digital output which may be used as an MCU port expander. This signal is low when the Port bit (C1) of the C register is low, and high when the Port bit is high. OUTPUT B Open-Drain Digital Output (Pin 15) This signal is a general-purpose digital output which may be used as an MCU port expander. This signal is low when the Out B bit (C0) of the C register is low. When the Out B bit is high, OUTPUT B assumes the high-impedance state. OUTPUT B may be pulled up through an external resistor or active circuitry to any voltage less than or equal to the potential of the VPD pin. Note: the maximum voltage allowed on the VPD pin is 9.5 V for the MC145200 and 5.5 V for the MC145201. Upon power-up, power-on reset circuitry forces OUTPUT B to a low level. REFERENCE PINS REFin and REFout Reference Input and Reference Output (Pins 20 and 1) Configurable pins for a Crystal or an External Reference. This pair of pins can be configured in one of two modes: the crystal mode or the reference mode. Bits R13, R14, and R15 in the R register control the modes as shown in Figure 17. In crystal mode, these pins form a reference oscillator when connected to terminals of an external parallel-resonant crystal. Frequency-setting capacitors of appropriate values as recommended by the crystal supplier are connected from each of the two pins to ground (up to a maximum of 30 pF each, including stray capacitance). An external resistor of 1 M to 15 M is connected directly across the pins to ensure linear operation of the amplifier. The device is designed to operate with crystals up to 15 MHz; the required connections are shown in Figure 8. To turn on the oscillator, bits R15, R14, and R13 must have an octal value of one (001 in binary, respectively). This is the active-crystal mode shown in Figure 17. In this mode, the crystal oscillator runs and the R Counter divides the crystal frequency, unless the part is in standby. If the part is placed in standby via the C register, the oscillator runs, but the R counter is stopped. However, if bits R15 to R13 have a value of 0, the oscillator is stopped, which saves additional power. This is the shut-
down crystal mode (shown in Figure 17) and can be engaged whether in standby or not. In the reference mode, REFin (Pin 20) accepts a signal up to 27 MHz from an external reference oscillator, such as a TCXO. A signal swinging from at least the VIL to VIH levels listed in the Electrical Characteristics table may be directly coupled to the pin. If the signal is less than this level, ac coupling must be used as shown in Figure 8. Due to an on- board resistor which is engaged in the reference modes, an external biasing resistor tied between REFin and REFout is not required. With the reference mode, the REFout pin is configured as the output of a divider. As an example, if bits R15, R14, and R13 have an octal value of seven, the frequency at REFout is the REFin frequency divided by 16. In addition, Figure 17 shows how to obtain ratios of eight, four, and two. A ratio of one-to-one can be obtained with an octal value of three. Upon power up, a ratio of eight is automatically initialized. The maximum frequency capability of the REFout pin is 10 MHz. Therefore, for REFin frequencies above 10 MHz, the one-to-one ratio may not be used. Likewise, for REFin frequencies above 20 MHz, the ratio must be more than two. If REFout is unused, an octal value of two should be used for R15, R14, and R13 and the REFout pin should be floated. A value of two allows REFin to be functional while disabling REFout, which minimizes dynamic power consumption and electromagnetic interference (EMI). LOOP PINS fin and fin Frequency Inputs (Pins 11 and 10) These pins are frequency inputs from the VCO. These pins feed the on-board RF amplifier which drives the 64/65 prescaler. These inputs may be fed differentially. However, they usually are used in a single-ended configuration (shown in Figure 7). Note that fin is driven while fin must be tied to ground via a capacitor. Motorola does not recommend driving fin while terminating fin because this configuration is not tested for sensitivity. The sensitivity is dependent on the frequency as shown in the Loop Specifications table. PDout Single-Ended Phase/Freq. Detector Output (Pin 6) This is a three-state current-source/sink output for use as a loop error signal when combined with an external low-pass filter. The phase/frequency detector is characterized by a linear transfer function (no dead zone). The operation of the phase/ frequency detector is described below and is shown in Figure 18. POL bit (C7) in the C register = low (see Figure 15) Frequency of fV > fR or Phase of fV Leading fR: current- sinking pulses from a floating state Frequency of fV < fR or Phase of fV Lagging fR: current- sourcing pulses from a floating state Frequency and Phase of fV = fR: essentially a floating state; voltage at pin determined by loop filter POL bit (C7) = high Frequency of fV > fR or Phase of fV Leading fR: current- sourcing pulses from a floating state Frequency of fV < fR or Phase of fV Lagging fR: current- sinking pulses from a floating state
MOTOROLA
MC145200*MC145201 9
Frequency and Phase of fV = fR: essentially a floating state; voltage at pin determined by loop filter This output can be enabled, disabled, and inverted via the C register. If desired, PDout can be forced to a floating state by utilization of the disable feature in the C register (bit C6). This is a patented feature. Similarly, PDout is forced to the floating state when the device is put into standby (STBY bit C4 = high). The PDout circuit is powered by VPD. The phase detector gain is controllable by bits C3, C2, and C1: gain (in amps per radian) = PDout current divided by 2. R and V (Pins 3 and 4) Double-Ended Phase/Frequency Detector Outputs These outputs can be combined externally to generate a loop error signal. Through use of a Motorola patented technique, the detector's dead zone has been eliminated. Therefore, the phase/frequency detector is characterized by a linear transfer function. The operation of the phase/frequency detector is described below and is shown in Figure 18. POL bit (C7) in the C register = low (see Figure 15) Frequency of fV > fR or Phase of fV Leading fR: V = negative pulses, R = essentially high Frequency of fV < fR or Phase of fV Lagging fR: V = essentially high, R = negative pulses Frequency and Phase of fV = fR: V and R remain essentially high, except for a small minimum time period when both pulse low in phase POL bit (C7) = high Frequency of fV > fR or Phase of fV Leading fR: R = negative pulses, V = essentially high Frequency of fV < fR or Phase of fV Lagging fR: R = essentially high, V = negative pulses Frequency and Phase of fV = fR: V and R remain essentially high, except for a small minimum time period when both pulse low in phase These outputs can be enabled, disabled, and interchanged via C register bits C6 or C4. This is a patented feature. Note that when disabled or in standby, R and V are forced to their rest condition (high state). The R and V output signal swing is approximately from GND to VPD. LD Lock Detector Output (Pin 2) This output is essentially at a high level with narrow low- going pulses when the loop is locked (fR and fV of the same phase and frequency). The output pulses low when fV and fR are out of phase or different frequencies. LD is the logical ANDing of R and V (see Figure 18). This output can be enabled and disabled via the C register. This is a patented feature. Upon power up, on-chip initialization circuitry disables LD to a static low logic level to prevent a false "lock" signal. If unused, LD should be disabled and left open. The LD output signal swing is approximately from GND to VDD.
Rx External Resistor (Pin 8) A resistor tied between this pin and GND, in conjunction with bits in the C register, determines the amount of current that the PD out pin sinks and sources. When bits C2 and C3 are both set high, the maximum current is obtained at PD out; see Tables 2 and 3 for other values of current. To achieve a maximum current of 2 mA, the resistor should be about 47 k when V PD is 9 V or about 18 k when VPD is 5.0 V. See Figure 14 if lower maximum current values are desired. When the R and V outputs are used, the Rx pin may be floated. TEST POINT PINS TEST 1 Modulus Control Signal (Pin 9) This pin may be used in conjunction with the Test 2 pin for access to the on-board 64/65 prescaler. When Test 1 is low, the prescaler divides by 65. When high, the prescaler divides by 64. CAUTION This pin is an unbuffered output and must be floated in an actual application. This pin must be attached to an isolated pad with no trace. TEST 2 Prescaler Output (Pin 13) This pin may be used to access to the on-board 64/65 prescaler output. CAUTION This pin is an unbuffered output and must be floated in an actual application. This pin must be attached to an isolated pad with no trace. POWER SUPPLY PINS VDD Positive Power Supply (Pin 14) This pin supplies power to the main CMOS digital portion of the device. The voltage range is + 4.5 to + 5.5 V with respect to the GND pin. For optimum performance, VDD should be bypassed to GND using a low-inductance capacitor mounted very close to these pins. Lead lengths on the capacitor should be minimized. VCC Positive Power Supply (Pin 12) This pin supplies power to the RF amp and 64/65 prescaler. The voltage range is + 4.5 to + 5.5 V with respect to the GND pin. In the standby mode, the VCC pin still draws a few milliamps from the power supply. This current drain can be eliminated with the use of transistor Q1 as shown in Figure 22. For optimum performance, VCC should be bypassed to GND using a low-inductance capacitor mounted very close to these pins. Lead lengths on the capacitor should be minimized.
MC145200*MC145201 10
MOTOROLA
VPD Positive Power Supply (Pin 5) This pin supplies power to both phase/frequency detectors A and B. The voltage applied on this pin must be no less than the potential applied to the VDD pin. The maximum voltage can be + 9.5 V with respect to the GND pin for the MC145200 and + 5.5 V for the MC145201.
For optimum performance, VPD should be bypassed to GND using a low-inductance capacitor mounted very close to these pins. Lead lengths on the capacitor should be minimized. GND Ground (Pin 7) Common ground.
100 ns MINIMUM
ENB
CLK 1 2 3 4 5 1 2 3 4 5 1 2 3 4 5
Din
NOTE: It may not be convenient to control the ENB or CLK pins during power up per the Pin Descriptions. If this is the case, the part may be initialized through the serial port as shown in the figure above. The sequence is similar to accessing the registers except that the CLK must remain high at least 100 ns after ENB is brought high. Note that 3 groups of 5 bits are needed.
Figure 13. Initializing the PLL through the Serial Port
MC145200 Nominal PDout Spurious Current vs fR Frequency (1 V PDout VPD - 1V)
t
t
MC145201 Nominal PDout Spurious Current vs fR Frequency (1 V PDout VPD - 1V)
t
t
fR (kHz) 10 20 50 100 200
Current (RMS nA) 1.6 5.3 22 95 320
fR (kHz) 10 20 50 100 200
Current (RMS nA) 3.6 4.6 17 75 244
NOTE: For information on spurious current measurement see AN1253/D, "An Improved PLL Design Method Without n and ".
Table 2. PDout Current, C1 = Low with OUTPUT A NOT Selected as "Port"; Also, Default Mode When OUTPUT A Selected as "Port"
C3 0 0 1 1 C2 0 1 0 1 PDout Current 70% 80% 90% 100%
Table 3. PDout Current, C1 = High with OUTPUT A NOT Selected as "Port"
C3 0 0 1 1 C2 0 1 0 1 PDout Current 25% 50% 75% 100%
MOTOROLA
MC145200*MC145201 11
180 170 160 150 140 130 Rx, EXTERNAL RESISTOR (k ) 120 110 100 90 80 70 60 50 40 30 20 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 Iout, SOURCE CURRENT (mA) 1.8 1.9 2.0 2.1 2.2 2.3 VPD = 9.5 V VPD = 8.75 V VPD = 8.0 V PDout CURRENT SET TO 100%; PDout VOLTAGE IS FORCED TO ONE-HALF OF VPD.
Nominal MC145200 PDout Source Current vs Rx Resistance
100 90 80 70 Rx, EXTERNAL RESISTOR (k ) 60 50 40 30 20 10 0 0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3 Iout, SOURCE CURRENT (mA) VPD = 5.5 V VPD = 5.0 V VPD = 4.5 V PDout CURRENT SET TO 100%; PDout VOLTAGE IS FORCED TO ONE-HALF OF VPD.
Nominal MC145201 PDout Source Current vs Rx Resistance
NOTE: The MC145201 is optimized for Rx values in the 18 k to 40 k range. For example, to achieve 0.3 mA of output current, it is preferable to use a 30-k resistor for Rx and bit settings for 25% (as shown in Table 3).
Figure 14.
MC145200*MC145201 12
MOTOROLA
ENB
CLK
1
2
3
4
5
6
7
8
*
MSB Din C7 C6 C5 C4 C3 C2 C1
LSB C0
* At this point, the new byte is transferred to the C register and stored. No other registers are affected. C7 -- POL: Selects the output polarity of the phase/frequency detectors. When set high, this bit inverts the polarity of PDout and interchanges the R function with V as depicted in Figure 18. Also see the phase detector output pin descriptions for more information. This bit is cleared low at power up. Selects which phase/frequency detector is to be used. When set high, enables the output of phase/ frequency detector A (PDout) and disables phase/frequency detector B by forcing R and V to the static high state. When cleared low, phase/frequency detector B is enabled (R and V) and phase/frequency detector A is disabled with PDout forced to the high-impedance state. This bit is cleared low at power up. Enables the lock detector output (LD) when set high. When the bit is cleared low, the LD output is forced to a static low level. This bit is cleared low at power up. When set high, places the CMOS section of device, which is powered by the VDD and VPD pins, in the standby mode for reduced power consumption: PDout is forced to the high-impedance state, R and V are forced high, the A, N, and R counters are inhibited from counting, and the Rx current is shut off. In standby, the state of LD is determined by bit C5. C5 low forces LD low (no change). C5 high forces LD static high. During standby, data is retained in the A, R, and C registers. The condition of REF/OSC circuitry is determined by the control bits in the R register: R13, R14, and R15. However, if REFout = static low is selected, the internal feedback resistor is disconnected and the input is inhibited when in standby; in addition, the REFin input only presents a capacitive load. NOTE: Standby does not affect the other modes of the REF/OSC circuitry. When C4 is reset low, the part is taken out of standby in 2 steps. First, the REFin (only in one mode) resistor is reconnected, all counters are enabled, and the Rx current is enabled. Any fR and fV signals are inhibited from toggling the phase/frequency detectors and lock detector. Second, when the first fV pulse occurs, the R counter is jam loaded, and the phase/frequency and lock detectors are initialized. Immediately after the jam load, the A, N, and R counters begin counting down together. At this point, the fR and fV pulses are enabled to the phase and lock detectors. (Patented feature.) C3, C2 -- I2, I1: C1 -- Port: Controls the PDout source/sink current per Tables 2 and 3. With both bits high, the maximum current (as set by Rx per Figure 14) is available. Also, see C1 bit description. When the OUTPUT A pin is selected as "Port" via bits A22 and A23, C1 determines the state of OUTPUT A. When C1 is set high, OUTPUT A is forced high; C1 low forces OUTPUT A low. When OUTPUT A is NOT selected as "Port," C1 controls whether the PDout step size is 10% or 25%. (See Tables 2 and 3.) When low, steps are 10%. When high, steps are 25%. Default is 10% steps when OUTPUT A is selected as "Port." The Port bit is not affected by the standby mode. Determines the state of OUTPUT B. When C0 is set high, OUTPUT B is high-impedance; C0 low forces OUTPUT B low. The Out B bit is not affected by the standby mode. This bit is cleared low at power up.
C6 -- PDA/B:
C5 -- LDE: C4 -- STBY:
C0 -- Out B:
Figure 15. C Register Access and Format (8 Clock Cycles are Used)
MOTOROLA
MC145200*MC145201 13
ENB
Figure 16. A Register Access and Format (24 Clock Cycles are Used)
CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC CCC
LSB A21 A20 A19 A18 A17 A16 A15 A14 A13 A12 A11 A10 A9 A8 A7 A6 A5 A4 A3 A2 A1 A0 1 BOTH BITS MUST BE HIGH 1 0 0 0 0 . . . 3 3 0 1 2 3 . . . E F A COUNTER A COUNTER A COUNTER A COUNTER = /0 = /1 = /2 = /3 0 0 0 0 0 0 0 0 . . . F F F F E F N COUNTER = / 4094 N COUNTER = / 4095 0 0 0 0 0 0 0 0 . . . 0 1 2 3 4 5 6 7 . . . NOT ALLOWED NOT ALLOWED NOT ALLOWED NOT ALLOWED NOT ALLOWED N COUNTER = / 5 N COUNTER = / 6 N COUNTER = / 7 A COUNTER = / 62 A COUNTER = / 63 4 4 . . . F HEXADECIMAL VALUE FOR N COUNTER 0 1 . . . F NOT ALLOWED NOT ALLOWED NOT ALLOWED HEXADECIMAL VALUE FOR A COUNTER
MC145200*MC145201 14
2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24
NOTE 3
CLK
1
MSB
D in
A23
A22
0 0 1 1
0 1 0 1
PORT D out fV fR
BINARY OUTPUT A VALUE FUNCTION (NOTE 1)
NOTES: 1. A power-on initialize circuit forces the OUTPUT A function to default to Data Out. 2. The values programmed for the N counter must be greater than or equal to the values programmed for the A counter. This results in a total divide value = N x 64 + A. 3. At this point, the three new bytes are transferred to the A register. In addition, the 13 LSBs in the first buffer of the R register are transferred to the R register's second buffer. Thus, the R, N, and A counters can be presented new divide ratios at the same time. The first buffer of the R register is not affected. The C register is not affected.
MOTOROLA
ENB
CLK
1 MSB
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16 LSB
NOTE NOTE 4 5
Din
R15
R14
R13
R12
R11
R10
R9
R8
R7
R6
R5
R4
R3
R2
R1
R0
0 CRYSTAL MODE, SHUT DOWN 1 CRYSTAL MODE, ACTIVE 2 REFERENCE MODE, REFin ENABLED and REFout STATIC LOW 3 REFERENCE MODE, REFout = REFin (BUFFERED) 4 REFERENCE MODE, REFout = REFin/2 5 REFERENCE MODE, REFout = REFin/4 6 REFERENCE MODE, REFout = REFin/8 (NOTE 3) 7 REFERENCE MODE, REFout = REFin/16 OCTAL VALUE
0 0 0 0 0 0 0 0 0 * * * 1 1
0 0 0 0 0 0 0 0 0 * * * F F
0 0 0 0 0 0 0 0 0 * * * F F
0 1 2 3 4 5 6 7 8 * * * E F
NOT ALLOWED R COUNTER = / 1 (NOTE 6) NOT ALLOWED NOT ALLOWED NOT ALLOWED R COUNTER = / 5 R COUNTER = / 6 R COUNTER = / 7 R COUNTER = / 8
R COUNTER = / 8190 R COUNTER = / 8191
BINARY VALUE
HEXADECIMAL VALUE
NOTES: 1. Bits R15 through R13 control the configurable "OSC or 4-stage divider" block (see Block Diagram). 2. Bits R12 through R0 control the "13-stage R counter" block (see Block Diagram). 3. A power-on initialize circuit forces a default REFin to REFout ratio of eight. 4. At this point, bits R13, R14, and R15 are stored and sent to the "OSC or 4-Stage Divider" block in the Block Diagram. Bits R0 through R12 are loaded into the first buffer in the double-buffered section of the R register. Therefore, the R counter divide ratio is not altered yet and retains the previous ratio loaded. The C and A registers are not affected. 5. At this point, bits R0 through R12 are transferred to the second buffer of the R register. The R counter begins dividing by the new ratio after completing the rest of the present count cycle. CLK must be low during the ENB pulse, as shown. Also, see note 3 of Figure 16 for an alternate method of loading the second buffer in the R register. The C and A registers are not affected. The first buffer of the R register is not affected. 6. Allows direct access to reference input of phase/frequency detectors.
Figure 17. R Register Access and Format (16 Clock Cycles Are Used)
MOTOROLA
MC145200*MC145201 15
fR REFERENCE REFin / R fV FEEDBACK fin / (N x 64 + A)
VH VL VH VL
*
PDout R V
SOURCING CURRENT FLOAT SINKING CURRENT VH VL VH VL VH
LD VL VH = High voltage level VL = Low voltage level *At this point, when both fR and fV are in phase, the output source and sink circuits are turned on for a short interval. NOTE: The PDout either sources or sinks current during out-of-lock conditions. When locked in phase and frequency, the output is high impedance and the voltage at that pin is determined by the low-pass filter capacitor. PDout, R, and V are shown with the polarity bit (POL) = low; see Figure 14 for POL.
Figure 18. Phase/Frequency Detectors and Lock Detector Output Waveforms
DESIGN CONSIDERATIONS
CRYSTAL OSCILLATOR CONSIDERATIONS The following options may be considered to provide a reference frequency to Motorola's CMOS frequency synthesizers. Use of a Hybrid Crystal Oscillator Commercially available temperature-compensated crystal oscillators (TCXOs) or crystal-controlled data clock oscillators provide very stable reference frequencies. An oscillator capable of CMOS logic levels at the output may be direct or dc coupled to REFin. If the oscillator does not have CMOS logic levels on the outputs, capacitive or ac coupling to REFin may be used (see Figure 8). For additional information about TCXOs and data clock oscillators, please consult the latest version of the eem Electronic Engineers Master Catalog, the Gold Book, or similar publications. Design an Off-Chip Reference The user may design an off-chip crystal oscillator using discrete transistors or ICs specifically developed for crystal oscillator applications, such as the MC12061 MECL device. The reference signal from the MECL device is ac coupled to REFin (see Figure 8). For large amplitude signals (standard CMOS logic levels), dc coupling may be used. Use of the On-Chip Oscillator Circuitry The on-chip amplifier (a digital inverter) along with an appropriate crystal may be used to provide a reference source
frequency. A fundamental mode crystal, parallel resonant at the desired operating frequency, should be connected as shown in Figure 19. The crystal should be specified for a loading capacitance (CL) which does not exceed approximately 20 pF when used at the highest operating frequency of 15 MHz. Assuming R1 = 0 , the shunt load capacitance (CL ) presented across the crystal can be estimated to be: CinCout Cin+Cout C1 C2 C1 + C2
CL = where
+ Ca + Cstray +
Cin = 5 pF (see Figure 20) Cout = 6 pF (see Figure 20) Ca = 1 pF (see Figure 20) C1 and C2 = external capacitors (see Figure 19) Cstray = the total equivalent external circuit stray capacitance appearing across the crystal terminals The oscillator can be "trimmed" on-frequency by making a portion or all of C1 variable. The crystal and associated components must be located as close as possible to the REFin and REFout pins to minimize distortion, stray capacitance, stray inductance, and startup stabilization time. Circuit stray capacitance can also be handled by adding the appropriate stray value to the values for Cin and Cout. For this approach, the term Cstray becomes 0 in the above expression for CL.
MC145200*MC145201 16
MOTOROLA
Power is dissipated in the effective series resistance of the crystal, Re, in Figure 21. The maximum drive level specified by the crystal manufacturer represents the maximum stress that the crystal can withstand without damage or excessive shift in operating frequency. R1 in Figure 19 limits the drive level. The use of R1 is not necessary in most cases. To verify that the maximum dc supply voltage does not cause the crystal to be overdriven, monitor the output frequency (fR) at OUTPUT A as a function of supply voltage. (REFout is not used because loading impacts the oscillator.) The frequency should increase very slightly as the dc supply voltage is increased. An overdriven crystal decreases in frequency or becomes unstable with an increase in supply voltage. The operating supply voltage must be reduced or R1 must be increased in value if the overdriven condition exists. The user should note that the oscillator start-up time is proportional to the value of R1. Through the process of supplying crystals for use with CMOS inverters, many crystal manufacturers have developed expertise in CMOS oscillator design with crystals. Discussions with such manufacturers can prove very helpful (see Table 4). RECOMMENDED READING Technical Note TN-24, Statek Corp. Technical Note TN-7, Statek Corp. E. Hafner, "The Piezoelectric Crystal Unit-Definitions and Method of Measurement", Proc. IEEE, Vol. 57, No. 2, Feb. 1969. D. Kemper, L. Rosine, "Quartz Crystals for Frequency Control", Electro-Technology, June 1969. P. J. Ottowitz, "A Guide to Crystal Selection", Electronic Design, May 1966. D. Babin, "Designing Crystal Oscillators", Machine Design, March 7, 1985. D. Babin, "Guidelines for Crystal Oscillator Design", Machine Design, April 25, 1985.
FREQUENCY SYNTHESIZER
REFin
Rf R1*
REFout
C1
C2
* May be needed in certain cases. See text.
Figure 19. Pierce Crystal Oscillator Circuit
Ca REFin Cin Cstray Cout REFout
Figure 20. Parasitic Capacitances of the Amplifier and Cstray
CS 2
RS 1 2 1
LS
CO 1 Re Xe 2
NOTE: Values are supplied by crystal manufacturer (parallel resonant crystal).
Figure 21. Equivalent Crystal Networks
Table 4. Partial List of Crystal Manufacturers
Motorola -- Internet Address http://motorola.com United States Crystal Corp. Crystek Crystal Statek Corp. Fox Electronics NOTE: Motorola cannot recommend one supplier over another and in no way suggests that this is a complete listing of crystal manufacturers. (Search for resonators)
MOTOROLA
MC145200*MC145201 17
PHASE-LOCKED LOOP -- LOW-PASS FILTER DESIGN
K KVCO NC R 2 K KVCOC N nRC 2
(A)
PDout R C
VCO
n =
=
=
Z(s) =
1 + sRC sC
NOTE: For (A), using K in amps per radian with the filter's impedance transfer function, Z(s), maintains units of volts per radian for the detector/ filter combination. Additional sideband filtering can be accomplished by adding a capacitor C across R. The corner c = 1/RC should be chosen such that n is not significantly affected.
(B) R V R1 R2 C R1 - +
R2 C A VCO = n =
K KVCO NCR1 nR2C 2
ASSUMING GAIN A IS VERY LARGE, THEN: F(s) = R2sC + 1 R1sC
NOTE: For (B), R1 is frequently split into two series resistors; each resistor is equal to R1 divided by 2. A capacitor CC is then placed from the midpoint to ground to further filter the error pulses. The value of CC should be such that the corner frequency of this network does not significantly affect n. * The R and V outputs are fed to an external combiner/loop filter. The R and V outputs swing rail-to-rail. Therefore, the user should be careful not to exceed the common mode input range of the op amp used in the combiner/loop filter. DEFINITIONS: N = Total Division Ratio in Feedback Loop K (Phase Detector Gain) = IPDout / 2 amps per radian for PDout K (Phase Detector Gain) = VPD / 2 volts per radian for V and R 2fVCO KVCO (VCO Transfer Function) = radians per volt VVCO For a nominal design starting point, the user might consider a damping factor 0.7 and a natural loop frequency n (2fR/50) where fR is the frequency at the phase detector input. Larger n values result in faster loop lock times and, for similar sideband filtering, higher fR-related VCO sidebands. Either loop filter (A) or (B) is frequently followed by additional sideband filtering to further attenuate fR-related VCO sidebands. This additional filtering may be active or passive. RECOMMENDED READING: Gardner, Floyd M., Phaselock Techniques (second edition). New York, Wiley-Interscience, 1979. Manassewitsch, Vadim, Frequency Synthesizers: Theory and Design (second edition). New York, Wiley-Interscience, 1980. Blanchard, Alain, Phase-Locked Loops: Application to Coherent Receiver Design. New York, Wiley-Interscience, 1976. Egan, William F., Frequency Synthesis by Phase Lock. New York, Wiley-Interscience, 1981. Rohde, Ulrich L., Digital PLL Frequency Synthesizers Theory and Design. Englewood Cliffs, NJ, Prentice-Hall, 1983. Berlin, Howard M., Design of Phase-Locked Loop Circuits, with Experiments. Indianapolis, Howard W. Sams and Co., 1978. Kinley, Harold, The PLL Synthesizer Cookbook. Blue Ridge Summit, PA, Tab Books, 1980. Seidman, Arthur H., Integrated Circuits Applications Handbook, Chapter 17, pp. 538-586. New York, John Wiley & Sons. Fadrhons, Jan, "Design and Analyze PLLs on a Programmable Calculator," EDN. March 5, 1980. AN535, Phase-Locked Loop Design Fundamentals, Motorola Semiconductor Products, Inc., 1970. AR254, Phase-Locked Loop Design Articles, Motorola Semiconductor Products, Inc., Reprinted with permission from Electronic Design, 1987. AN1253/D, An Improved PLL Design Method Without n and , Motorola Semiconductor Products, Inc., 1995.
MC145200*MC145201 18
MOTOROLA
THRESHOLD DETECTOR 1 REF out INTEGRATOR OPTIONAL LOOP ERROR SIGNALS (NOTE 1) +V LOW-PASS FILTER 2 LD 3 R 4 V 5 6 7 8 NC 9 10 1000 pF UHF VCO VPD PDout GND Rx TEST 1 fin REFin 20
+5 V
Din 19 18 CLK ENB OUTPUT A OUTPUT B VDD TEST 2 VCC 17 16 15 14 13 12 NC +5 V GENERAL-PURPOSE DIGITAL OUTPUT
MCU
Q1 NOTE 2
fin 11
UHF OUTPUT BUFFER NOTES: 1. When used, the R and V outputs are fed to an external combiner/loop filter. See the Phase- Locked Loop -- Low-Pass Filter Design page for additional information. 2. Transistor Q1 is required only if the standby feature is needed. Q1 permits the bipolar section of the device to be shut down via use of the general-purpose digital pin, OUTPUT B. If the standby feature is not needed, tie Pin 12 directly to the power supply. 3. For optimum performance, bypass the VCC, VDD, and VPD pins to GND with low-inductance capacitors. 4. The R counter is programmed for a divide value = REFin/fR. Typically, fR is the tuning resolution required for the VCO. Also, the VCO frequency divided by fR = NT = N x 64 + A; this determines the values (N, A) that must be programmed into the N and A counters, respectively.
Figure 22. Example Application
DEVICE #1 Din CLK ENB OUTPUT A (DATA OUT) Din
DEVICE #2 CLK ENB OUTPUT A (DATA OUT)
CMOS MCU OPTIONAL NOTE: See related Figures 24 through 26; these bit streams apply to the MC145190, MC145191, MC145200, and MC145201.
Figure 23. Cascading Two Devices
MOTOROLA
MC145200*MC145201 19
ENB
Figure 25. Accessing the A Registers of Two Cascaded Devices
8 15 16 17 23 9 10 24 25 A23 A22 A16 A15 A8 A7 A REGISTER BITS OF DEVICE #2 IN FIGURE 23
CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC
A0 A23 A16 A9 A8 A0 A REGISTER BITS OF DEVICE #1 IN FIGURE 23
Figure 24. Accessing the C Registers of Two Cascaded Devices
2 7 8 9 10 15 16 17 18 23 24 25 26 31 32 33 34 39 X X C7 C6 C0 X X X X X X C7 C6 C REGISTER BITS OF DEVICE #2 IN FIGURE 23 31 32 33 39 40 46 47 48
ENB
CLK
D in
MOTOROLA
*At this point, the new bytes are transferred to the A registers of both devices and stored. Additionally, for both devices, the 13 LSBs in each of the first buffers of the R registers are transferred to the respective R register's second buffer. Thus, the R, N, and A counters can be presented new divide ratios at the same time. The first buffer of each R register is not affected. Neither C register is affected.
CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC
C0 C REGISTER BITS OF DEVICE #1 IN FIGURE 23
MC145200*MC145201 20
40 55 56
CLK
1
*
D in
X
*At this point, the new bytes are transferred to the C registers of both devices and stored. No other registers are affected.
*
1
2
X
X
Figure 26. Accessing the R Registers of Two Cascaded Devices
CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC CC
R15 R14 R8 R7 R0 X X R15 R8 R7 R0 R REGISTER BITS OF DEVICE #2 IN FIGURE 23 R REGISTER BITS OF DEVICE #1 IN FIGURE 23
MOTOROLA
NOTE 1 NOTE 2 8 15 16 17 23 24 25 31 32 33 9 10 39 40 41 47 48
ENB
CLK
1
2
D in
X
X
NOTES APPLICABLE TO EACH DEVICE: 1. At this point, bits R13, R14, and R15 are stored and sent to the "OSC or 4-Stage Divider" block in the Block Diagram. Bits R0 through R12 are loaded into the first buffer in the doublebuffered section of the R register. Therefore, the R counter divide ratio is not altered yet and retains the previous ratio loaded. The C and A registers are not affected. 2. At this point, the bits R0 through R12 are transferred to the second buffer of the R register. The R counter begins dividing by the new ratio after completing the rest of the present count cycle. CLK must be low during the ENB pulse, as shown. Also, see note of Figure 25 for an alternate method of loading the second buffer in the R register. The C and A registers are not affected. The first buffer of the R register is not affected.
MC145200*MC145201 21
PACKAGE DIMENSIONS
F SUFFIX SOG (SMALL OUTLINE GULL-WING) PACKAGE CASE 751J-02
-A20 11
-B1 10
J
G S
10 PL
K
M
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSIONS A AND B DO NOT INCLUDE MOLD PROTRUSION. 4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE. 5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.13 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION. DIM A B C D G J K L M S MILLIMETERS MIN MAX 12.55 12.80 5.40 5.10 2.00 -- 0.45 0.35 1.27 BSC 0.23 0.18 0.85 0.55 0.20 0.05 7 0 7.40 8.20 INCHES MIN MAX 0.494 0.504 0.201 0.213 0.079 -- 0.014 0.018 0.050 BSC 0.007 0.009 0.022 0.033 0.002 0.008 7 0 0.291 0.323
0.13 (0.005)
B
M
C D
20 PL M
L TB
S
0.10 (0.004) -TA
S SEATING PLANE
M
0.13 (0.005)
DT SUFFIX TSSOP (THIN SHRUNK SMALL OUTLINE PACKAGE) CASE 948D-03 A
20X
K REF 0.200 (0.004)
M
T
20
11
L
PIN 1 IDENTIFICATION 1 10
B
C -U0.100 (0.004) -TSEATING PLANE
NOTES: 1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982. 2. CONTROLLING DIMENSION: MILLIMETER. 3. DIMENSION A DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. MOLD FLASH OR GATE BURRS SHALL NOT EXCEED 0.15 (0.006) PER SIDE. 4. DIMENSION B DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSION. INTERLEAD FLASH OR PROTRUSION SHALL NOT EXCEED 0.25 (0.010) PER SIDE. 5. DIMENSION K DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.08 (0.003) TOTAL IN EXCESS OF THE K DIMENSION AT MAXIMUM MATERIAL CONDITION. 6. TERMINAL NUMBERS ARE SHOWN FOR REFERENCE ONLY. 7. DIMENSIONS A AND B ARE TO BE DETERMINED AT DATUM PLANE -U-. MILLIMETERS MIN MAX --- 6.60 4.30 4.50 --- 1.20 0.05 0.25 0.45 0.55 0.65 BSC 0.275 0.375 0.09 0.24 0.09 0.18 0.16 0.32 0.16 0.26 6.30 6.50 0 10 INCHES MIN MAX --- 0.260 0.169 0.177 --- 0.047 0.002 0.010 0.018 0.022 0.026 BSC 0.011 0.015 0.004 0.009 0.004 0.007 0.006 0.013 0.006 0.010 0.248 0.256 0 10
D
G
H
K J1 J SECTION A-A A F K1
A M
DIM A B C D F G H J J1 K K1 L M
MC145200*MC145201 22
MOTOROLA
Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. "Typical" parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including "Typicals" must be validated for each customer application by customer's technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer.
Mfax is a trademark of Motorola, Inc. How to reach us: USA / EUROPE / Locations Not Listed: Motorola Literature Distribution; P.O. Box 5405, Denver, Colorado 80217. 1-303-675-2140 or 1-800-441-2447 MfaxTM: RMFAX0@email.sps.mot.com - TOUCHTONE 1-602-244-6609 Motorola Fax Back System - US & Canada ONLY 1-800-774-1848 - http://sps.motorola.com/mfax/ HOME PAGE: http://motorola.com/sps/ JAPAN: Nippon Motorola Ltd.: SPD, Strategic Planning Office, 141, 4-32-1 Nishi-Gotanda, Shagawa-ku, Tokyo, Japan. 03-5487-8488 ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park, 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852-26629298 CUSTOMER FOCUS CENTER: 1-800-521-6274
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MC145200/D MC145200*MC145201 23

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